Consider a general tu o-conductor transmission line for which the conductors have a (round-trip) series resistance per unit length \(R_{1}\) and the medium between conductors has a leakage conductance per unit length \(G_{1}\). Show that the valtage and current waves then obey the telegrapher's equalion $$ \frac{\partial^{s} v}{\partial s^{2}}=L_{1} C_{3} \frac{\partial^{s} v}{\partial r^{2}}+\left(R_{1} C_{1}+G_{1} L_{1}\right) \frac{\partial v}{\partial t}+R_{1} G_{1} v $$ What can you discover about the solutions of this equation? Show that the characteristic impedance for monochromatic waves is $$ \breve{Z}_{0}=\left(\frac{R_{1}+j \omega L_{1}}{G_{1}+j \omega C_{1}}\right)^{1 / 2} $$

Short Answer

Expert verified
The solutions of the telegrapher's equation represent wave propagation in both forward and backward directions in the transmission line due to the presence of second-order time and space derivatives. Additionally, the equation is linear, meaning that any linear combination of the solutions is also a solution. This allows for the application of superposition principles to solve more complex scenarios.

Step by step solution

01

Derive the telegrapher's equation in the given form

The telegrapher's equations are a pair of coupled partial differential equations that describe the voltage and current on an electrical transmission line. Generally, they can be written as: $$ \frac{\partial v}{\partial z} = - (R_1 + j\omega L_1) i $$ $$ \frac{\partial i}{\partial z} = - (G_1 + j\omega C_1) v $$ We want to eliminate the current \(i\), so we can do that by differentiating the first equation with respect to \(z\), getting: $$ \frac{\partial^2 v}{\partial z^2} = - (R_1 + j\omega L_1) \frac{\partial i}{\partial z} $$ Now, we substitute the second telegrapher's equation for \(\frac{\partial i}{\partial z}\): $$ \frac{\partial^2 v}{\partial z^2} = - (R_1 + j\omega L_1) (-(G_1 + j\omega C_1) v) $$ Now, expand the product: $$ \frac{\partial^2 v}{\partial z^2} = L_1 C_1 \frac{\partial^2 v}{\partial t^2} + (R_1 C_1 + G_1 L_1) \frac{\partial v}{\partial t} + R_1 G_1 v $$ This is the telegrapher's equation in the given form.
02

Discuss the properties of the solutions

The telegrapher's equation we derived is a second-order linear partial differential equation, and its solutions describe the propagation of voltage and current waves in the transmission line. Since the equation contains second-order time and space derivatives, its solutions can represent wave propagation in both forward and backward directions. Additionally, since the equation is linear, superposition principles apply, which means that any linear combination of solutions is also a solution.
03

Find the characteristic impedance for monochromatic waves

For monochromatic waves, we consider a single frequency component of the voltage and current: $$ v(z,t) = V_0 e^{j(\omega t - \beta z)} $$ $$ i(z,t) = I_0 e^{j(\omega t - \beta z)} $$ Substituting these into the telegrapher's equations will result in: $$ -j \beta V_0 e^{j(\omega t - \beta z)} = - (R_1 + j\omega L_1) I_0 e^{j(\omega t - \beta z)} $$ $$ -j \beta I_0 e^{j(\omega t - \beta z)} = - (G_1 + j\omega C_1) V_0 e^{j(\omega t - \beta z)} $$ Dividing the first equation by the second one gives: $$ \frac{V_0}{I_0} = \frac{R_1 + j\omega L_1}{G_1 + j\omega C_1} $$ The ratio \(\frac{V_0}{I_0}\) is defined as the characteristic impedance of the transmission line. Therefore, the characteristic impedance for monochromatic waves can be written as: $$ \breve{Z}_0 = \left(\frac{R_1 + j\omega L_1}{G_1 + j\omega C_1}\right)^{1/2} $$

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Key Concepts

These are the key concepts you need to understand to accurately answer the question.

Transmission Line Theory
Transmission lines are the conduits responsible for conveying electrical energy from one point to another, often over long distances. They encompass a broad range of physical structures, such as coaxial cables, optical fibers, and power lines. The transmission line theory encompasses understanding the behavior of electrical signals as they travel through these lines.

In essence, it addresses the distribution of voltages and currents along the transmission line and predicts phenomena such as reflection, attenuation, and distortion of signals. To analyze these effects, a set of equations known as the telegrapher's equations are used. These equations are derived from the physical properties of the lines, including resistance, capacitance, inductance, and conductance per unit length.

Understanding these concepts allows engineers to design lines that minimize signal loss and maximize fidelity, ensuring that the power or data delivered at the end of the line closely matches what was sent, a critical aspect in various industries from telecommunications to power distribution.
Characteristic Impedance
The concept of characteristic impedance, denoted as \(Z_0\), plays a pivotal role in the functionality of transmission lines. It is a complex quantity representing the relationship between voltage and current in a transmission line during wave propagation. To put it simply, it defines how much resistance to electrical flow is encountered in the line.

The characteristic impedance is important because it determines reflection and refraction of waves at discontinuities along the line. If the impedance of the transmission line matches the impedance of the load, the energy is fully absorbed by the load, and no reflections occur. However, if these impedances do not match, some of the energy is reflected back, which can cause issues like signal loss or distortion.

Engineers use the characteristic impedance to ensure efficient power transfer and minimize reflections, which is vital in applications like radio antenna design, where mismatched impedances can greatly reduce the efficiency of energy transmission.
Wave Propagation
Wave propagation within transmission line theory refers to the movement of waveforms, such as voltage and current waves, along the line. These waves can be described by solving the telegrapher's equation, which takes into account both the electrical properties of the medium and the geometric properties of the line.

When an electrical signal is introduced into a transmission line, it propagates in the form of electromagnetic waves. The nature of these waves can be complex and is often affected by factors like the line’s composition, environment, and operating frequencies. For instance, at higher frequencies, wave propagation phenomena such as skin effect come into play, causing the signal to travel mostly on the outer surface of the conductor.

To ensure reliable communication, it is crucial to understand signal behaviors, like phase velocity and group delay, which are critical for managing time-sensitive data and ensuring that the integrity of the signal is preserved from source to destination.

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Most popular questions from this chapter

Consider an ionized gas of uniform electron density \(n\). Regard the positive ions as a smeared-out continuous fluid which renders the gas macroscopically neutral and through which the electrons can move without friction. Now assume that, by some external means, each electron is shifted in the \(x\) direction by the displacement \(\xi=\xi(x)\), a function of its initial, unperturbed location \(x\). (a) Show from Gauss' law (8.2.1) that the resulting electric field is \(E_{x}=n e \xi / e_{0} .(b)\) Show that each electron experiences a linear (Hooke's law) restoring force such that when the external forces are removed, it oscillates about the equilibrium position \(\xi=0\) with simple harmonic motion at the angular frequency $$ \omega_{p}=\left(\frac{n e^{2}}{\epsilon_{0} m}\right)^{1 / 2} $$ which is known as the electron plasma frequency. † For fuller discussion, see J. A. Ratcliffe, "The Magneto-ionic Theory and Its Applications to the Ionosphere," Cambridge University Press, New York, 1959 ; M. A. Heald and C. B. Wharton, "Plasma Diagnostics with Microwaves," John Wiley \& Sons Inc., New York, 1965; I. P. Shkarofsky, T. W. Johnson, and M. P. Bachynski, "Particle Kinetics of Plasma," Addison-Wesley Publishing Company, Reading, Mass., \(1965 .\)

For normal incidence and nonmagnetic materials show that the power coefficients \((8.6 .38)\) and \((8.6 .39)\) reduce to $$ \begin{aligned} &R_{p}=\left(\frac{n-1}{n+1}\right)^{x} \\ &T_{p}=\frac{4 n}{(n+1)^{2}} \end{aligned} $$ where \(n=c_{1} / c_{2}=Z_{01} / Z_{02}\) is the relative refractive index. Account for the difference in sign between the amplitude reflection coefficients \((8.6 .28)\) and \((8.6 .36)\) at normal incidence (see footnote, page 102). Compare with equations (1.9.6), (4.2.15), and (5.6.13).

Consider two unbounded plane waves whose vector wave numbers \(k_{1}\) and \(\kappa_{2}\left(\left.\right|_{1,2} \mid=\right.\) \(\omega / c)\) define a plane and whose electric fields are polarized normal to the plane. (a) Show that the superposition of these two plane waves is a wave traveling in the direction bisecting the angle \(\alpha\) between \({ }_{1}{ }_{1}\) and \({ }_{k}\) and that the \(\mathbf{E}\) field vanishes on a set of nodal planes spaced \(a=\) \(\lambda_{0} / 2 \sin \frac{1}{2} \alpha\) apart. \((b)\) Show that plane conducting walls can be placed at two adjacent nodal planes without violating the electromagnetic boundary conditions and likewise that a second pair of conducting walls of arbitrary separation \(b\) can be introduced to construct a rectangular waveguide of cross section \(a\) by \(b\), propagating the \(T E_{10}\) mode. Thus establish that the TE \(_{10}\) mode (more generally, the TE \(_{10}\) modes) may be interpreted as the superposition of two plane waves making the angle \(\frac{1}{2} \alpha\) with the waveguide axis and undergoing multiple reflections from the sidewalls. Note: The situation is directly analogous to that discussed in Sec. 2.4. Higherorder TE modes \((m>0)\) and TM modes may be described similarly as a superposition of four plane waves.

Consider total reflection at an interface between two nonmagnetic media, with relative refractive index \(n=c_{1} / c_{2}<1\). For angles of incidence \(\theta_{1}\) exceeding the critical angle of (8.6.42), Snell's law gives $$ \sin \theta_{2}=\frac{\sin \theta_{1}}{n}>1, $$ which implies that \(\theta_{2}\) is a complex angle with an imaginary cosine, $$ \cos \theta_{2}=\left(1-\sin ^{2} \theta_{2}\right)^{1 / 2}=j\left(\frac{\sin ^{2} \theta_{1}}{n^{2}}-1\right)^{1 / 2} $$ Substitute these relations in the case I reflection coefficient (8.6.28) to establish $$ R_{\mathbf{E} \perp}=e^{-i 2 \phi_{\perp}}, $$ where $$ \tan \phi_{\perp}=\frac{\left(\sin ^{2} \theta_{1}-n^{2}\right)^{1 / x}}{\cos \theta_{1}} $$ That is, the magnitude of the reflection coefficient is unity, but the phase of the reflected wave depends upon angle. Similarly show for case II from (8.6.36), that \(R_{\text {III }}=e^{-\text {jod with }}\) $$ \tan \phi \|=\frac{\left(\sin ^{2} \theta_{1}-n^{2}\right)^{1 / 2}}{n^{2} \cos \theta_{1}}=\frac{1}{n^{2}} \tan \phi_{\perp} . $$ Note that the two phase shifts are different, so that in general the state of polarization of an incident wave is altered.

Consider a plasma of electron density \(n\) immersed in a uniform static magnetic field \(\mathbf{B}_{0 .}\) Let \(\mathbf{B}_{0}\) be in the \(z\) direction. Revise the equation of motion (8.8.2) to include the Lorentz force \(q\left(\mathbf{v} \times \mathbf{B}_{0}\right)\) on the electrons (but drop the collision term for simplicity); write out the resulting equation in cartesian components. (a) Show that plane waves propagating in the \(x\) direction, say, but with the electric field polarized parallel to \(\mathbf{B}_{0}\), are unaffected by the presence of \(\mathrm{B}_{0}\). (b) Show that circularly polarized plane waves (see Prob. \(8.3 .5\) ) can propagate in the \(z\) direction with wave numbers $$ K=\frac{\omega}{c}\left[1-\frac{\omega_{p}^{2}}{\omega\left(\omega \pm \omega_{b}\right)}\right]^{1 / 2} $$ where \(\omega_{b} \equiv c B_{0} / m\) is the cyclotron frequency. (c) Show that a TM wave can propagate in the \(x\) direction with the wave magnetic field polarized parallel to \(\mathbf{B}_{\theta}\), with the wave number $$ k=\frac{\omega}{c}\left[1-\frac{\omega_{p}^{2}\left(\omega^{2}-\omega_{p}^{2}\right)}{\omega^{2}\left(\omega^{2}-\omega_{p}^{2}-\omega_{b}^{2}\right)}\right]^{1 / 2} $$

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